Frequency control and power balancing in disturbed power inverter system and method thereof

ABSTRACT

A system and method are disclosed for controlling DC to AC power converters (inverters) that are operated as voltage sources and are paralleled on the AC side. This method allows for controlling frequency while sharing real power. The disclosed method requires no communication between inverters for proper load sharing, thus enhancing reliability of a system of parallel inverters. The only signals required for control are the AC voltage and frequency and their reaction to the inverter output current. The present invention allows a multiplicity of inverters or active rectifiers to share power in relation to their share of the available power capacity of the system. This makes it possible to parallel DG sources with various response times while they are connected to either a utility grid or in a stand-alone power network with no communications required between inverters. The addition of communications to the system allows the dispatch of energy for economic reasons and to fine tune load balance. Communications can be used for systems status and maintenance but is not required for reliable short-term operation.

This application claims benefit of priority to Provisional Application60/585,407 dated Jul. 01, 2004.

FIELD OF INVENTION

This disclosure relates generally to electronic power inverter andespecially to a power inverter with frequency control and powerbalancing features in a disturbed power inverter system with applicationto distributed generation and demand side management.

BACKGROUND OF INVENTION

Many new types of distributed generation and energy storage products arecurrently being developed. These devices include, but are not limitedto: fuel cells, flywheels, advanced batteries, micro-turbines, Stirlingengines, wind turbines, solar cells and double-layer capacitors. Eachone of these devices requires a power electronic inverter at its outputto make useable AC power, typically 50 or 60 Hz single or three-phasepower.

The simplest model of parallel power converters on an AC grid consistsof two single-phase AC voltage sources 10, 12 operating at about thesame frequency connected to each other through an inductance 14, 16 asshown in FIG. 1. If both AC sources are at the same frequency, phase,and amplitude, there will be no current flowing between the sources, aswell as no power flow. A slight phase shift in either source will causereal power to flow from the leading source to the lagging source. If theamplitude is changed for either source, reactive power will then flowfrom the higher amplitude source to the lower amplitude source. Now, ifwe add a resistive load 18 between the two generators 10, 12 we canvisualize a more realistic AC power system. As the load 18 is increased(i.e., draws more current), there will be a phase shift between the loadand the AC voltage sources. If the sources are perfect voltage sources(i.e., having no power limits or output impedance), this will work welland adjusting the phase relationship can control the relative power fromeach source.

When the two sources are a synchronous type generator such as one drivenby an internal combustion engine, the system reacts differently. Whenthe load draws more power, the frequency of each generator will dropuntil a control system for the engine fuel system increases the engineoutput to bring the system power back into balance. In this situationthe power and frequency balances need to be controlled. Both sources aretrying to provide the correct frequency and speed. There are manytraditional solutions to this problem. If the machines are near eachother or there is high-speed communications between the machines, onemaster controller can schedule and control the fuel to each machine.Another method, called isochronous control, couples the output powersense and control signal through a set of signals in such way to makethe machines balance power. Both of these methods require high-speedcommunications or actual control wires between generators to controlsystem power balance and frequency.

Another method that does not use communications and is used frequentlyis frequency droop control. In this method each generator in a systemhas a frequency power schedule so that when the frequency is low theymake more power and when the frequency is high they make less power.This way the power outputs are balanced on a per unit basis for theconnected generators if the frequency droop factor is the same for eachmachine in proportion to its size. The frequency range needed for thistype of control depends on the accuracy with which the absolutefrequency can be determined by each controller. The frequency can varyas much as +/−3 Hz when using this method with small rotating machines.These basic concepts are used to control power systems of manysynchronous generators throughout utility power networks.

When controlling parallel inverters, one solution is to use the samedroop control methods used in synchronous generators. This is achievedby controlling real power or real current of the inverter in proportionto the frequency error. This has the same effect as the synchronousgenerator control described above. A typical inverter control system isshown in FIG. 2. It should be noted that the frequency error signal fromthe phase locked loop 20 (PLL) goes to the power command signal of theinverter controller 22.

Typically a second order PLL is used for this application. The secondorder PLL 20 provides very little phase error at any frequency ofoperation at steady state. Sometimes a first order PLL is used but thishas a phase error, which is a function of frequency. This phase errorcan be set to zero at any frequency by using the offset center frequencyas shown in FIG. 3.

It is considered advantageous to provide a distributed power inverterwhich could be applied to loads with active power converter front ends.In this way, certain dispatchable loads could help improve system powerand frequency control allowing better use of available generationcapacity by reducing the need for reserve power (spinning reserve).

Also, it is considered advantageous to provide uninterruptible powersupply (UPS) systems that consist of multiple devices operating togetherto provide the required systems functions, including operating inparallel both connected to and isolated from the utility grid to provideuninterrupted power to the connected loads.

SUMMARY OF THE INVENTION

A power control system including an inverter and inductive memberconnecting the inverter to an AC power network. An inverter controlsystem, wherein the inverter control system includes a phase lockedloop, whereby the input of the phase locked loop is the voltage at theAC power network side of the inverter and the output of the phase lockedloop is a sine wave corresponding to the desired fundamental value andphase at the output of said inverter. The phase locked loop may furtherinclude a transfer function providing a phase shift of 0.5 to 500degrees per Hz during nearly steady operation, said transfer functionbeing selected to provide a smaller phase shift when the output phaseangle changes suddenly. In the preferred embodiment, the phase shiftoccurs when the output phase angle changes in less than 0.1 seconds.

A method of controlling power output from a control system, includes thesteps of obtaining a phase error signal that represents the differencebetween the inverter and grid/load voltages. Generating a frequencyerror signal that is a function of the phase error signal, wherein saidphase error signal and frequency error signals are voltage signals.Adjusting the phase error signal via a feedback loop that includes aphase shift and filter of the frequency error signal. Adjusting thefrequency of the inverter by the use of the frequency error signal andfiltering the phase shift signal from a conventional phase-locked loopso as to generate a filtered phase shifted signal and generating saidfrequency error signal as a function of said filtered phase shiftedsignal.

The above discussed and other features will be appreciated andunderstood by those skilled in the art from the following detaileddescription and drawings.

BRIEF DESCRIPTION OF THE DRAWINGS

Referring now to the drawings, which are meant to be exemplary and notlimiting, and wherein like elements are numbered alike:

FIG. 1 is a diagram of a simplified prior art AC power system includingmultiple sources;

FIG. 2 is a schematic diagram of a prior art Single Phase Control Systemknow in the prior art;

FIG. 3 is a schematic diagram of a prior art phase locked loop (“PLL”);

FIG. 4 is a schematic diagram of a PLL of the present invention;

FIG. 5 is a Bode Plot of loop compensation of the present invention;

FIG. 6 is a schematic diagram of the PLL of the present invention in apower inverter application;

FIG. 7 is a schematic diagram of the PLL of the present invention with alow pass filter option.

DETAILED DESCRIPTION OF THE INVENTION

Referring to FIG. 4 and FIG. 6, a system for connecting to an electricalgrid and controlling a power inverter is shown. The system 43 includesat least one AC electrical power source 47 that is connected to anelectrical grid 49 having an inductance 51. A plurality of powerinverters 48 are connected to the electrical grid 49 through an inductor45. The electrical grid 49 may be a conventional utility grid, or anisolated power network. It should be appreciated that the inventiondisclosed herein is applicable to either a single phase or a three phaseelectrical system. The electrical grid 49 may optionally include aisolation switch 62 that removes the load 64 and power inverters 48 fromthe power source 47.

Each power inverter 48 is operated by a control system 60. The invertercontrol system 60 includes a controller 50 that provides the controlalgorithms and commands to the power inverter 48. In the preferredembodiment, the controller 50 implements the control code in a digitalsignal processor. Alternatively the controller 50 may be an analogcircuit. The controller 50 receives input signals 66, 68 from a phaselock loop circuit 26 in addition to a voltage 70 and current 72 feedbacksignals. The controller 50 may be the same as that described in U.S.Pat. No. 6,693,409 issued Feb. 17, 2004 entitled “Control System For aPower Converter and Method of Controlling Operation of a PowerConverter” which is incorporated herein by reference in its entirety forall relevant purposes.

The phase lock loop (PLL) circuit 26 is shown in more detail in FIG. 4.The PLL 26 receives a signal 74 representative of the electrical grid 49voltage into a phase detector circuit 42. The phase detector 42 combinesthe voltage signal 49 with the cosine output signal 68 to generate aphase error signal 76. The phase error signal 76 is transmitted tofeedback circuit 30.

The feedback circuit 30 includes a summation circuit 78 that iselectrically coupled and provides input to a loop filter 80. The loopfilter 80 outputs a frequency error signal 82 that is input into a phaseshift circuit 32 and low pass filter 28. As will be described in moredetail herein below, the phase shift and low pass filter signal 86 isinput into the summation circuit 78 to provide a feedback loop thatadjusts the phase error signal 84 received by the loop filter 80.

The frequency error signal 82 is provided to the input of summationcircuit 88 where it is combined with a center frequency signal 90. Thecenter frequency signal 90 is generated by operator selection software(not shown) and preferrably matches the AC electrical frequency of theelectrical grid 49. The output of the summation circuit 88 is receivedby a voltage controlled oscillator 40 (VCO). The input signal 90 is usedby the VCO 40 to provide a repeating sine 66 and cosine 68 waveformsignals that utilized by the controller 50 to provide phase andfrequency compensation.

The present invention makes it possible to connect any number of powerinverters 48 in parallel to the same AC power grid 49 without requiringinter-unit communication for real power and frequency stability. Whenthe PLL 26 in the inverter control system 60 is operated in this manner,the parallel inverters 48 balance power and frequency control. Thiscontrol is provided both when the inverters 48 are connected to theutility grid and when isolated from a prime mover such as a generator.When connected to a stiff frequency controlled system like a utilitygrid 49, the inverters 48 track frequency, and power can be controlledto any amount desired.

When the parallel inverters 48 are connected to a soft or uncontrolledfrequency source, the inverters 48 will balance power and trackfrequency and keep the frequency near the center frequency (typically 50or 60 Hz). This control method achieves the same effect as the frequencydroop control used in synchronous generators, but is much easier toimplement in an electronic power converter than traditional methods thatbase power commands on frequency error.

In the preferred embodiment a series inductor 45 is included on theoutput of the inverter 48. This allows the real power is controlled bycontrolling the phase shift across the inductor 45. Therefore thecontrol can be implemented in a feed forward manner, which providesenhanced response to changes and stability with some compromise in theprecision of the frequency droop factor due to inductor tolerance.

As discussed above, in the preferred embodiment a feed forward controlmethod used. Therefore, the traditional feedback from the frequency tothe power command can be used in conjunction with the present invention.This will provide the system both improved response and stability, aswell as accuracy, while compromising on complexity. In addition, thismethod can work on the load side of a system by adjusting the powerdrawn by a load based on efficiency. This is possible for loads 64 thathave active converter front ends. Active power converter front-endsystems are unusual, but may become more common as power electronicsbecomes lower cost and the technology advances.

As discussed above, the PLL 26 effectively controls the phase errorrelative to the frequency error independent of the PLL compensation andlow pass filter. It should be appreciated that the reference inputsignal 74 for the PLL 26 is from the grid 49 side of the inductor 45,and the output 66, 68 of the PLL 26 controls the voltage and currentphases of the inverter 48 side of the inductor 45. In the preferredembodiment, the PLL 26 is a second order PLL. The low pass filter 28 isincluded in the feedback circuit 40 so that the transient stability andthe tracking bandwidth of the PLL 26 is not changed by the feedbackgain. This will make the PLL 26 have a transfer function that tracksfast changes in frequency or phase but allows a small amount of phaseerror to build to balance power when the frequency begins to drift. ThePLL 26 described herein may be considered a hybrid between a first orderPLL and second order PLL. At high frequencies the PLL 26 behaves like asecond order PLL with high gain, and at low frequencies the PLL 26behaves like a first order PLL with low gain. It should be noted thatthis embodiment of the present invention includes the phase shift 32 andlow pass filter 28 applied to either a first or second order PLL forthis application. This provides the PLL 26 control loop low gain at lowfrequencies to control sharing and high gain at high frequencies toimprove dynamic tracking. Typical traditional PLLs are designed with thehighest possible gain at all frequencies to obtain good tracking and lowphase errors. In the preferred embodiment, DC phase errors are allowedto improve power sharing. It should be appreciated that the low passfilter 28 is optional, but is desirable to improve the performance ofthe PLL 26. In addition, alternative filters may be used in place of thelow pass filter.

In operation, in order for the AC power source 47 to send real powerinto a grid, the phase of the voltage output has to shift to lead thegrid voltage due to the inductive nature of the grid impedance 51. Inprior art inverter control systems, this was accomplished byimplementing a current control loop that responds to a current commandgenerated from a reference waveform that is derived from the gridvoltage. In this prior art system, the action of the current controlloop will force the output voltage at the terminal of the inverter to beas required so that the output current will match the desired currentwaveform (template). Then a frequency error signal is used to set thelevel of real current commanded to the grid in order to maintainfrequency sharing and stability (droop control) to the grid. The presentinvention provides at least two differences from the prior art system.First, the input voltage reference 74 (Vfb) for the PLL 26 comes fromthe grid 49 or load side of the inductor 45 but the inverter 48 outputis connected to the opposite side of the inductor 45. Second, in thepreferred embodiment, there is no current waveform used for frequencycontrol. The PLL 26 shifts the voltage reference waveforms in phase toshift the voltage across the output inductor 45. This action forces realcurrent through the output inductor 45 which then goes into theelectrical grid 49. By making the phase shift a function of frequencywithin the PLL 26 the present invention effectively performs theequivalent of droop control right in the PLL 26 without requiring theexternal current control loop.

These differences result in a number of advantages, including: 1) lesscomputational power is required in the control processor to perform thedroop function; 2) the frequency vs power droop performance is not assensitive to the other control systems in the inverter, specifically thecurrent and power controllers; 3) this method is much less sensitive toerror due the known filtering features of a phase locked loop, thefrequency signal of the PLL is very stable and well filtered making forstable noiseless power flow; and 4) the response of an inverter systemusing the present invention to power and frequency fluctuations willnaturally scale the output impedance on the inverter, meaning if theoutput impedance on the inverter is the same per unit then the per unitdroop will also scale.

Referring to FIG. 5, the frequency response of a prior art second orderPLL loop compensation 36 and the compensation 38 of the presentinvention are shown. It should be appreciated that the phase of thepresent invention's filter transitions from the response of the firstorder system at low frequencies to the second order system at higherfrequencies. Since the transfer function of the combination of the VCO40 and the phase detector 42 make an integrator for the remainder of thePLL 26 open loop response, therefore the PLL 26 will be stable forsituations where the gain bandwidth product of this integrator is about100 radians/sec (15.9 Hz).

It should be appreciated that the teachings of the present invention canbe applied to any type of power inverters operating in parallel with agrid or other inverters. The teachings of the present invention alsoapply to any type of frequency and phase detection system including anytype of phase locked loop.

Referring to FIG. 6, the PLL 26 of the present invention is shown. ThePLL 26 provides a constant phase shift versus frequency error. The valueof this phase shift per Hz (Kp) will be in the range of 0.5 degree perHz to 500 degrees per Hz depending on the output inductance of theinverter and the desired frequency control.

The value of Kp is given by:

$K_{p} = \frac{{Sin}^{- 1}\left( L_{pu} \right)}{\Delta\; f}$

Where Lpu is:

${Lpu} = \frac{2 \cdot \pi \cdot F \cdot L \cdot P_{r}}{V^{2}}$

And for small L (less than 10% per unit):Sin⁻¹(L _(pu))≅Lpu

Therefore:

${K_{p} \cong \frac{Lpu}{\Delta\; f}} = \frac{2 \cdot \pi \cdot F \cdot L \cdot P_{r}}{{V^{2} \cdot \Delta}\; f}$Where:

P_(r) is the inverter rated power;

L is the output inductance;

L_(pu) is the output inductance per unit;

V is the nominal voltage of the power system;

F is the nominal power system frequency (typically 50 or 60 Hz);

Δf is the frequency deviation at rated power; and

Kp is the phase shift gain in degrees or radians per Hz.

If the same Kp is used in each PLL 26 and the output inductors 45 aresized the same on a per unit basis, then all the inverters 48 inparallel will share power in proportion to their rating. The value of Kpcan be used to control which inverter 48 provides the most power whenoperating in is landed mode. For example: if one inverter 48 has ahigher Kp than others, it will tend to take more of the power changes inthe system 43 first. When this inverter 48 reaches its output limits theothers will then share the additional power.

An alternate embodiment for a plurality of parallel power converters isuse a power bias in conjunction with of droop control. In this way asource can have a bias of a certain amount of power over or under theother converters in the system rather than by simply a fraction of therating as when different units have different values for Kp. The powerbias is simply the real power commands 46 shown in FIG. 6.

An exemplary embodiment of the present invention will be described inreference to FIG. 7. In this embodiment, the PLL 51 includes a circuit58. The circuit 58 includes a loop filter 52, phase shift 56, low passfilter 54 and summation circuit 55. It should be appreciated that thecomponents 52, 54, 55, 56 are illustrated as separate components forpurposes of clarity, but preferably would be integrated into a singlecircuit. As will be made clearer herein below, the circuit 58 is shownmerely for the purpose of clearly illustrating the changes to the lowpass filter.

There are a number of options for the design of the loop filter 52. Thelow pass filter 54 choice a function of the loop filter 52characteristics. Consider a simple first order PLL. In this embodiment,the loop filter 52 could be as simple as a gain and a single pole looppass function. This is best described by a Laplace transform,

${T_{1}(s)} = \frac{K_{1}}{1 + \frac{s}{\omega_{1}}}$where:

-   -   T₁(s) is the transfer function of the prior art filter;    -   K₁ is the gain of that filter; and    -   ω₁ is the corner frequency of the filter.

In general, one skilled in the art would typically choose the value ofω₁ high enough to get keep system stable and low enough to filter thesecond harmonic of the operating frequency that will be output by mosttypes of phase detectors. The gain K₁ is chosen to give the desiredresponse time. Higher values yield faster response but require highervalues of ω₁ for stability.

The additional gain and low pass filter 58 of the exemplary embodimentcan be described similarly as

${T_{2}(s)} = \frac{K_{2}}{1 + \frac{s}{\omega_{2}}}$where:

-   -   T₂(s) is the transfer function of the gain and the filter block        added in the model;    -   K₂ is the gain of the phase shift block and is equivalent to the        gain value;    -   K_(p) is the phase shift gain in degrees or radians per Hz as        described above; and    -   ω₂ is the corner frequency of the low pass filter block.

The choice of K_(p) is described herein above and the choice of thevalue for ω₂ depends on intended performance and the other parameters aswill be described herein below. In the preferred embodiment, the valueof ω₂ is much lower than ω₁.

The transfer function of the gain and filter circuit 58 can be derivedas follows:

${T_{f}(s)} = {\frac{O(s)}{I(s)} = {\frac{{T_{1}(s)}*\left( {{I(s)} - {{T_{2}(s)}*{O(s)}}} \right)}{I(s)} = \frac{1}{\frac{1}{T_{1}(s)} + {T_{2}(s)}}}}$

This is simply another type of low pass with a specific gain. Thetransfer function of this circuit 58 is shown below.

${T_{f}(s)} = \frac{K_{1} \cdot \omega_{1} \cdot \left( {\omega_{2} + s} \right)}{{\left( {\omega_{1} + s} \right) \cdot \left( {\omega_{2} + s} \right)} + {K_{1} \cdot K_{2} \cdot \omega_{1} \cdot \omega_{2}}}$

In the above transfer function if s=0, then

${T_{f}(s)} = {\frac{K_{1}}{1 + {K_{1} \cdot K_{2}}}.}$

In general there are two requirements of the low pass filter 54. Thefirst the gain at DC (s=0) is the appropriate value to leave a smallfrequency and phase error. In the preferred embodiment, this value is inthe range of 0.001 to 2 Hertz per degree, more preferrably, the valuesare in the range of 0.003 to 0.03 Hertz per degree. As discussed above,the assumption is made that K₁ is large and so the filter gain is simply1/K₂.

The second requirement is that the PLL 51 have fast tracking andresponse time to step changes in phase. This is accomplished in thepreferred embodiment by having higher gain in the loop filter at ACfrequencies making the bandwidth of the PLL 51 greater. The curves shownin FIG. 5 illustrates that this higher gain occurs at about 100 radiansper second.

The resulting PLL 51 of the exemplary embodiment would have a largephase error and slow frequency tracking and therefore be considered apoor design. However, when applied in the application shown in FIG. 6,these normally undesirable characteristics cause some very desirablesystem results, including: fast dynamics, very simple design and precisefrequency droop control.

While the invention has been described with reference to a preferredembodiment, it will be understood by those skilled in the art thatvarious changes may be made and equivalents may be substituted forelements thereof without departing from the scope of the invention. Inaddition, many modifications may be made to adapt a particular situationor material to the teachings of the invention without departing from theessential scope thereof. Therefore, it is intended that the inventionnot be limited to the particular embodiment disclosed as the best modecontemplated for carrying out this invention.

1. An electrical power control system comprising: a first inverter; anelectrical power grid; a first inductive member connected in seriesbetween said first inverter and said electrical power grid; a firstvoltage signal line between said electrical power grid and said firstinductive member; a first current signal line between said firstinductive member and said first inverter; a phase locked loop includingan input, an output and a transfer function providing a predeterminedphase shift between 0.5 to 500 degrees per Hz during nearly steadyoperation, said phase locked loop input is connected to said firstvoltage signal line said phase locked loop including means forgenerating a sine wave corresponding to the desired fundamental valueand phase at the output of said first inverter; and, a first invertercontrol system having an a first input coupled to said phased lock loopoutput, a second input coupled to said first voltage signal line, and athird input coupled to said first current signal loop.
 2. The electricalpower control system of claim 1 wherein said transfer function isselected to provide a smaller phase shift when the output phase anglechanges in less than 0.1 seconds.
 3. The electrical power control systemof claim 1 wherein the phase locked loop is a first order phase lockedloop.
 4. The electrical power control system of claim 1 wherein thephased locked loop is a second order phase locked loop.
 5. Theelectrical power control system of claim 4 further comprising a phaseshift electrically connected to said phase locked loop and said low passfilter.
 6. The electrical power control system of claim 5 furthercomprising a summation circuit electrically coupled to said low passfilter and a phase detector.
 7. The electrical power control system ofclaim 1 further comprising: a second inverter electrically coupled tosaid electric power grid; a second inductive member connected in seriesbetween said second inverter and said electrical power grid; a secondvoltage signal line between said electrical power grid and said secondinductive member; a second current signal line between said secondinductive member and said first inverter; a second phase locked loopincluding an input, an output and a transfer function providing apredetermined phase shift, whereby said second phase locked loop inputis connected to said second voltage signal line and said phase lockedloop includes means for generating a sine wave corresponding to thedesired fundamental value and phase at the output of said secondinverter.
 8. A method of controlling power output from a control systemhaving an inductor and a load, comprising the steps of: receiving asignal representative of voltage from an electrical grid on the loadside of the inductor; receiving a signal representative of voltage froman inverter coupled to the grid downstream from the inductor; obtaininga phase error signal that represents the difference between the inverterand electrical grid voltages; generating a frequency error signal thatis a function of the phase error signal, wherein said phase error signaland frequency error signals are voltage signals; adjusting the phaseerror signal via a feedback loop that includes a phase shift and lowpass filter of the frequency error signal; and, shifting the phasebetween 0.5 to 500 degrees per Hz during nearly steady operation.
 9. Themethod of controlling power output from a control system of claim 8comprising the step of adjusting the frequency of the inverter by theuse of the frequency error signal.
 10. The method of controlling poweroutput from a control system of claim 9 comprising the step of filteringthe phase shift signal from a phase-locked loop.
 11. The method ofcontrolling power output from a control system of claim 10 comprisingthe step of generating a filtered phase shifted signal and generatingsaid frequency error signal as a function of said filtered phase shiftedsignal.
 12. The method of controlling power output from a control systemof claim 11 comprising the step of generating a sine output and a cosinesignal from said filtered phase shifted signal.
 13. The method ofcontrolling power output from a control system of claim 12 comprisingthe step of receiving said sine and cosine signal in a control system.14. The method of controlling power output from a control system ofclaim 13 comprising the step of altering the output of an inverter basedon the sine and cosine signal.